Synchronous reset and phase detecting for interchain local oscillator (lo) divider phase alignment

ABSTRACT

Certain aspects of the present invention provide methods and apparatus for synchronizing frequency-divided oscillating signals associated with multiple radio frequency (RF) paths to be in-phase. For certain aspects, a reset pulse is input to synchronization logic for a particular RF path, and this logic retimes the reset pulse to a local synthesizer clock in this RF path. The retimed reset pulse drives the reset input of a local frequency divider for this RF path and is also appropriately delayed, buffered, and then daisy-chained to the synchronization logic in the next RF path to be repeated therein. By appropriately resetting the local frequency dividers using the synchronization logic in this manner, the frequency-divided oscillating signals for the RF paths are synchronized to operate in-phase with one another.

CLAIM OF PRIORITY

This application claims the benefit of U.S. Provisional PatentApplication Ser. No. 62/069,628, entitled “SYNCHRONOUS RESET AND PHASEDETECTING FOR INTERCHAIN LOCAL OSCILLATOR (LO) DIVIDER PHASE ALIGNMENT”and filed Oct. 28, 2014, and is a continuation-in-part of U.S. patentapplication Ser. No. 14/495,183, entitled “PHASE DETECTING CIRCUIT FORINTERCHAIN LOCAL OSCILLATOR (LO) DIVIDER PHASE ALIGNMENT” and filed Sep.24, 2014, pending, both of which are herein incorporated by reference intheir entireties.

TECHNICAL FIELD

Certain aspects of the present invention generally relate to radiofrequency (RF) electronic circuits and, more particularly, to phasealigning a plurality of signals and/or detecting phase shift betweensignals for phase alignment.

BACKGROUND

Wireless communication networks are widely deployed to provide variouscommunication services such as telephony, video, data, messaging,broadcasts, and so on. Such networks, which are usually multiple accessnetworks, support communications for multiple users by sharing theavailable network resources. For example, one network may be a wirelesslocal area network (WLAN) in accordance with the Institute of Electricaland Electronics Engineers (IEEE) 802.11 standard (e.g., Wi-Fi) or awireless personal area network (WPAN) in accordance with the IEEE 802.15standard. Another example wireless network may be a 3G (the thirdgeneration of mobile phone standards and technology), 4G, or latergeneration system, which may provide network service via any one ofvarious radio access technologies (RATs) including EVDO (Evolution-DataOptimized), 1×RTT (1 times Radio Transmission Technology, or simply 1×),W-CDMA (Wideband Code Division Multiple Access), UMTS-TDD (UniversalMobile Telecommunications System-Time Division Duplexing), HSPA (HighSpeed Packet Access), GPRS (General Packet Radio Service), or EDGE(Enhanced Data rates for Global Evolution). The 3G network is a widearea cellular telephone network that evolved to incorporate high-speedinternet access and video telephony, in addition to voice calls.Furthermore, a 3G network may be more established and provide largercoverage areas than other network systems. Such multiple access networksmay also include code division multiple access (CDMA) systems, timedivision multiple access (TDMA) systems, frequency division multipleaccess (FDMA) systems, orthogonal frequency division multiple access(OFDMA) systems, single-carrier FDMA (SC-FDMA) networks, 3^(rd)Generation Partnership Project (3GPP) Long Term Evolution (LTE)networks, and Long Term Evolution Advanced (LTE-A) networks.

A wireless communication network may include a number of base stationsthat can support communication for a number of mobile stations. A mobilestation (MS) may communicate with a base station (BS) via a downlink andan uplink. The downlink (or forward link) refers to the communicationlink from the base station to the mobile station, and the uplink (orreverse link) refers to the communication link from the mobile stationto the base station. A base station may transmit data and controlinformation on the downlink to a mobile station and/or may receive dataand control information on the uplink from the mobile station.

Certain radio frequency front-ends (RFFEs) have multiple receiver (RX)paths, multiple transmitter (TX) paths, or multiple transceiver paths,also known as chains. Each of these paths in a multi-chain RFFE may haveits own local oscillator (LO). The various LOs may be generated from asingle voltage-controlled oscillator (VCO) using, for example, adivide-by-2 (Div2), divide-by-3 (Div3), or divide-by-4 (Div4) frequencydivider associated with each path. Although all of the frequencydividers may output the same frequency LO, each divider may arbitrarilystart-up either in-phase (0°) or out-of-phase (180°) relative to anotherdivider in the case of Div2, or having a phase shift of 0°, 60°, 120°,180°, 240°, or 300° relative to another divider in the case of Div3. Inorder to achieve particular capabilities or perform certain functions,such as beamforming, it may be desirable to operate the dividersin-phase.

Accordingly, what is needed are techniques and apparatus for detectingwhether two high frequency input signals are in-phase or out-of-phaseand adjusting at least one of the two signals if these signals areout-of-phase. Alternatively or additionally, what is needed aretechniques and apparatus for phase aligning a plurality of highfrequency signals to be in-phase.

SUMMARY

Certain aspects of the present invention generally relate to detectingand adjusting phase shift between signals, such as local oscillatingsignals of adjacent receiver, transmitter, or transceiver pathsfrequency divided down from a voltage-controlled oscillator (VCO)signal. In this manner, all local oscillating signals may be adjusted tobe in-phase.

In accordance with certain aspects of the present invention, a circuitfor phase detection is described. The circuit generally includes a mixerconfigured to mix a first input signal having a first frequency with asecond input signal having a second frequency to produce an outputsignal having frequency components at the sum of and the differencebetween the first frequency and the second frequency, wherein the firstfrequency is the same as the second frequency; a filter connected withthe output signal produced by the mixer and configured to remove one ofthe frequency components at the sum of the first frequency and thesecond frequency, thereby leaving a direct current (DC) component; andan analog-to-digital converter (ADC) connected with the DC componentfrom the filter and configured to determine whether the first inputsignal is in-phase or out-of-phase with the second input signal based ona comparison between the DC component and a reference signal.

According to certain aspects, the first, second, and output signals aredifferential signals. In this case, the filter may include a capacitorto shunt a first output signal and a second output signal of adifferential pair for the output signal to generate a first DC componentand a second DC component, respectively. For certain aspects, the ADCmay be a comparator (e.g., a 1-bit ADC), and the comparator may beconfigured to compare the first output signal to the second outputsignal, where the second output signal is the reference signal. In thiscase, the comparator may output a logic HIGH to indicate that the firstinput signal is in-phase with the second input signal if the first DCcomponent has a greater amplitude than the second DC component, and thecomparator may output a logic LOW to indicate the first input signal isout-of-phase with the second input signal if the second DC component hasa greater amplitude than the first DC component.

According to certain aspects, a first expected phase shift rangecorresponding to the first input signal being in-phase with the secondinput signal leads to an amplitude of the DC component being above afirst threshold for the ADC. A second expected phase shift rangecorresponding to the first input signal being out-of-phase with thesecond input signal may lead to the amplitude of the DC component beingbelow a second threshold for the ADC.

For certain aspects, the mixer includes a Gilbert cell.

For certain aspects, the ADC is a clocked regenerative comparator.

According to certain aspects, the ADC is a multi-bit ADC configured toprovide information in addition to a determination whether the firstinput signal is in-phase or out-of-phase with the second input signal.For certain aspects, the information indicates a degree to which thefirst and second input signals are phase shifted.

In accordance with certain aspects of the present invention, a circuitfor wireless communications is described. The circuit generally includesa first transceiver path having a first local oscillating signal with afirst frequency; a second transceiver path having a second localoscillating signal with a second frequency, wherein the first frequencyis the same as the second frequency; and a first phase detectorconnected with the first transceiver path and the second transceiverpath. The first phase detector typically includes a first mixerconfigured to mix the first local oscillating signal with the secondlocal oscillating signal to produce a first output signal havingfrequency components at the sum of and the difference between the firstfrequency and the second frequency; a first filter connected with thefirst mixer and configured to remove one of the frequency components atthe sum of the first frequency and the second frequency, thereby leavinga first direct current (DC) component; and a first analog-to-digitalconverter (ADC) connected with the first filter and configured todetermine whether the first local oscillating signal is in-phase orout-of-phase with the second local oscillating signal based on acomparison between the first DC component and a first reference signal.

According to certain aspects, the first transceiver path includes afirst frequency divider configured to divide a frequency of avoltage-controlled oscillator (VCO) signal to produce the first localoscillating signal. The second transceiver path may include a secondfrequency divider configured to divide the frequency of the VCO signalto produce the second local oscillating signal. For certain aspects, thecircuit further includes a repeater configured to regenerate the VCOsignal. In this case, the second frequency divider may be configured toproduce the second local oscillating signal from the regenerated VCOsignal.

According to certain aspects, the circuit further includes a phaseshifter configured to phase shift the first local oscillating signal orthe second local oscillating signal if the first ADC determines that thefirst local oscillating signal is out-of-phase with the second localoscillating signal.

According to certain aspects, the circuit further includes a thirdtransceiver path having a third local oscillating signal with a thirdfrequency, wherein the first frequency is the same as the thirdfrequency, and a second phase detector connected with the secondtransceiver path and the third transceiver path. The second phasedetector may include a second mixer configured to mix the second localoscillating signal with the third local oscillating signal to produce asecond output signal having frequency components at the sum of and thedifference between the second frequency and the third frequency; asecond filter configured to receive the second output signal produced bythe second mixer and to remove one of the frequency components at thesum of the second frequency and the third frequency, thereby leaving asecond DC component; and a second ADC connected with the second filterand configured to receive the second DC component from the second filterand to determine whether the second local oscillating signal is in-phaseor out-of-phase with the third local oscillating signal based on acomparison between the second DC component and a second referencesignal. For certain aspects, the third transceiver path includes a thirdfrequency divider configured to divide the frequency of the VCO signalto produce the third local oscillating signal.

According to certain aspects, the first local oscillating signal, thesecond local oscillating signal, and the first output signal aredifferential signals. In this case, the first filter may include acapacitor configured to shunt signals of a differential pair for thefirst output signal to generate a second DC component and a third DCcomponent, respectively. For certain aspects, the first ADC is acomparator, and the comparator may be configured to compare the signalsof the differential pair for the first output signal. The comparator mayoutput a logic HIGH to indicate that the first local oscillating signalis in-phase with the second local oscillating signal if the second DCcomponent has a greater amplitude than the third DC component.Alternatively, the comparator may output a logic LOW to indicate thefirst local oscillating signal is out-of-phase with the second localoscillating signal if the third DC component has a greater amplitudethan the second DC component.

For certain aspects, the first mixer includes a Gilbert cell mixer.

For certain aspects, the first ADC is a clocked regenerative comparator.

According to certain aspects, the ADC is a multi-bit ADC configured toprovide information in addition to a determination whether the firstlocal oscillating signal is in-phase or out-of-phase with the secondlocal oscillating signal. For certain aspects, the information indicatesa degree to which the first and second local oscillating signals arephase shifted.

In accordance with certain aspects of the present invention, a methodfor detecting phase shift between signals is described. The methodgenerally includes mixing a first input signal having a first frequencywith a second input signal having a second frequency to produce anoutput signal having frequency components at the sum of and thedifference between the first frequency and the second frequency, whereinthe first frequency is the same as the second frequency; filtering theoutput signal to remove one of the frequency components at the sum ofthe first frequency and the second frequency, thereby leaving a DCcomponent; comparing the DC component to a reference signal; anddetermining whether the first input signal is in-phase or out-of-phasewith the second input signal based on the comparison.

In accordance with certain aspects of the present invention, anapparatus for detecting phase shift between signals is described. Theapparatus generally includes means for mixing a first input signalhaving a first frequency with a second input signal having a secondfrequency to produce an output signal having frequency components at thesum of and the difference between the first frequency and the secondfrequency, wherein the first frequency is the same as the secondfrequency; means for filtering the output signal to remove one of thefrequency components at the sum of the first frequency and the secondfrequency, thereby leaving a DC component; means for comparing the DCcomponent to a reference signal; and means for determining whether thefirst input signal is in-phase or out-of-phase with the second inputsignal based on the comparison.

Certain aspects of the present invention generally relate tosynchronizing signals, such as local oscillating signals of adjacentreceiver, transmitter, or transceiver paths frequency divided down froma voltage-controlled oscillator (VCO) signal. In this manner, all localoscillating signals in the various paths may be phase aligned.

In accordance with certain aspects of the present invention, a method isdescribed for synchronizing frequency-divided oscillating signalsassociated with multiple transceiver paths to be in-phase. The methodgenerally includes providing a first oscillating signal for a firsttransceiver path; receiving a first global reset signal; delaying thefirst global reset signal by clocking with the first oscillating signalto generate a first local reset signal synchronized to the firstoscillating signal; frequency dividing the first oscillating signal togenerate a first frequency-divided signal for the first transceiverpath, wherein the first local reset signal resets the frequency dividingof the first oscillating signal; outputting a second global reset signalsynchronized to the first oscillating signal; providing a secondoscillating signal for a second transceiver path, wherein the secondoscillating signal has the same frequency as the first oscillatingsignal; delaying the second global reset signal by clocking with thesecond oscillating signal to generate a second local reset signalsynchronized to the second oscillating signal; and frequency dividingthe second oscillating signal to generate a second frequency-dividedsignal for the second transceiver path, wherein the second local resetsignal resets the frequency dividing of the second oscillating signalsuch that the second frequency-divided signal is in phase with the firstfrequency-divided signal.

In accordance with certain aspects of the present invention, a circuitis described for synchronizing frequency-divided oscillating signalsassociated with multiple transceiver paths to be in-phase. The circuitgenerally includes a first distribution circuit configured to provide afirst oscillating signal for a first transceiver path; firstsynchronization logic configured to receive a first global reset signal;to delay the first global reset signal by clocking with the firstoscillating signal to generate a first local reset signal synchronizedto the first oscillating signal, and to output a second global resetsignal synchronized to the first oscillating signal; a first frequencydivider configured to frequency divide the first oscillating signal togenerate a first frequency-divided signal for the first transceiverpath, wherein the first local reset signal is configured to reset thefirst frequency divider; a second distribution circuit configured toprovide a second oscillating signal for a second transceiver path,wherein the second oscillating signal has the same frequency as thefirst oscillating signal; second synchronization logic configured todelay the second global reset signal by clocking with the secondoscillating signal to generate a second local reset signal synchronizedto the second oscillating signal; and a second frequency dividerconfigured to frequency divide the second oscillating signal to generatea second frequency-divided signal for the second transceiver path,wherein the second local reset signal is configured to reset the secondfrequency divider such that the second frequency-divided signal is inphase with the first frequency-divided signal.

According to certain aspects, the circuit further includes a frequencysynthesizer configured to generate a synthesized oscillating signal. Forcertain aspects, the first distribution circuit includes a bufferconfigured to buffer the synthesized oscillating signal to provide thefirst oscillating signal. For certain aspects, the first distributioncircuit includes a repeater configured to regenerate the synthesizedoscillating signal, or a regenerated version thereof, from a thirdtransceiver path. The first synchronization logic may be configured toreceive the first global reset signal in response to the frequencysynthesizer starting up or changing one or more operating parameters.

According to certain aspects, the first synchronization logic isconfigured to receive the first global reset signal from a thirdtransceiver path. The first global reset signal may be synchronized to athird oscillating signal for the third transceiver path.

According to certain aspects, the second oscillating signal is derivedfrom the first oscillating signal.

According to certain aspects, the first synchronization logic isconfigured to output the second global reset signal by delaying thefirst global reset signal via clocking with the first oscillating signala multiple of a least common multiple (LCM) between divisor options forthe first frequency divider. For certain aspects, the divisor optionsare 2 and 3, the LCM is 6, and the first global reset signal is delayed6 times by clocking 6 cascaded delay (D) flip-flops with the firstoscillating signal.

According to certain aspects, the circuit further includes a thirddistribution circuit configured to provide a third oscillating signalfor a third transceiver path, wherein the third oscillating signal hasthe same frequency as the first oscillating signal and the secondoscillating signal and wherein the second synchronization logic isconfigured to output a third global reset signal synchronized to thesecond oscillating signal; third synchronization logic configured todelay the third global reset signal by clocking with the thirdoscillating signal to generate a third local reset signal synchronizedto the third oscillating signal; and a third frequency dividerconfigured to frequency divide the third oscillating signal to generatea third frequency-divided signal for the third transceiver path, whereinthe third local reset signal is configured to reset the third frequencydivider such that the third frequency-divided signal is in phase withthe first frequency-divided signal and the second frequency-dividedsignal. The first transceiver path may be adjacent to the secondtransceiver path, and the second transceiver path may be adjacent to thethird transceiver path.

According to certain aspects, the first transceiver path is adjacent tothe second transceiver path.

According to certain aspects, the first frequency divider is configuredto divide a frequency of the first oscillating signal by at least one of2 or 3.

In accordance with certain aspects of the present invention, anapparatus is described for synchronizing frequency-divided oscillatingsignals associated with multiple transceiver paths to be in-phase. Theapparatus generally includes means for providing a first oscillatingsignal for a first transceiver path; means for receiving a first globalreset signal; means for delaying the first global reset signal byclocking with the first oscillating signal to generate a first localreset signal synchronized to the first oscillating signal; means forfrequency dividing the first oscillating signal to generate a firstfrequency-divided signal for the first transceiver path, wherein thefirst local reset signal is configured to reset the means for frequencydividing the first oscillating signal; means for outputting a secondglobal reset signal synchronized to the first oscillating signal; meansfor providing a second oscillating signal for a second transceiver path,wherein the second oscillating signal has the same frequency as thefirst oscillating signal; means for delaying the second global resetsignal by clocking with the second oscillating signal to generate asecond local reset signal synchronized to the second oscillating signal;and means for frequency dividing the second oscillating signal togenerate a second frequency-divided signal for the second transceiverpath, wherein the second local reset signal is configured to reset themeans for frequency dividing the second oscillating signal such that thesecond frequency-divided signal is in phase with the firstfrequency-divided signal.

BRIEF DESCRIPTION OF THE DRAWINGS

So that the manner in which the above-recited features of the presentinvention can be understood in detail, a more particular description,briefly summarized above, may be had by reference to aspects, some ofwhich are illustrated in the appended drawings. It is to be noted,however, that the appended drawings illustrate only certain typicalaspects of the present invention and are therefore not to be consideredlimiting of its scope, for the description may admit to other equallyeffective aspects.

FIG. 1 illustrates an example wireless communications network inaccordance with various aspects of the present invention.

FIG. 2 is a block diagram of an example access point (AP) and userterminals in accordance with various aspects of the present invention.

FIG. 3 is a block diagram of an example transceiver front-end inaccordance with various aspects of the present invention.

FIG. 4 illustrates an example phase detecting circuit for determiningwhether two input signals are in-phase or out-of-phase in accordancewith various aspects of the present invention.

FIG. 5 illustrates multiple example radio frequency (RF) chains, eachgenerating a local oscillating signal, and the circuit of FIG. 4 fordetecting phase shifts between local oscillating signals from twoadjacent RF chains, in accordance with various aspects of the presentinvention.

FIG. 6 is an example graph of a difference between two differentialdirect current (DC) component amplitudes across the filter in the phasedetecting circuit of FIG. 4 versus phase offset, in accordance withvarious aspects of the present invention.

FIG. 7 is a flow diagram of example operations for detecting phase shiftbetween signals in accordance with various aspects of the presentinvention.

FIG. 8 illustrates multiple example RF chains, each generating andfrequency dividing a local oscillating signal, and synchronization logicfor implementing a synchronized reset to achieve phase alignment of thefrequency-divided oscillating signals, in accordance with variousaspects of the present invention.

FIG. 9 illustrates an example implementation of the synchronizationlogic in FIG. 8 in accordance with various aspects of the presentinvention.

FIG. 10 is a flow diagram of example operations for synchronizingfrequency-divided oscillating signals associated with multipletransceiver paths to be in-phase in accordance with various aspects ofthe present invention.

DETAILED DESCRIPTION

Various aspects of the present invention are described below. It shouldbe apparent that the teachings herein may be embodied in a wide varietyof forms and that any specific structure, function, or both beingdisclosed herein is merely representative. Based on the teachingsherein, one skilled in the art should appreciate that an aspectdisclosed herein may be implemented independently of any other aspectsand that two or more of these aspects may be combined in various ways.For example, an apparatus may be implemented or a method may bepracticed using any number of the aspects set forth herein. In addition,such an apparatus may be implemented or such a method may be practicedusing other structure, functionality, or structure and functionality inaddition to or other than one or more of the aspects set forth herein.Furthermore, an aspect may comprise at least one element of a claim.

The word “exemplary” is used herein to mean “serving as an example,instance, or illustration.” Any aspect described herein as “exemplary”is not necessarily to be construed as preferred or advantageous overother aspects.

The techniques described herein may be used in combination with variouswireless technologies such as Code Division Multiple Access (CDMA),Orthogonal Frequency Division Multiplexing (OFDM), Time DivisionMultiple Access (TDMA), Spatial Division Multiple Access (SDMA), SingleCarrier Frequency Division Multiple Access (SC-FDMA), Time DivisionSynchronous Code Division Multiple Access (TD-SCDMA), and the like.Multiple user terminals can concurrently transmit/receive data viadifferent (1) orthogonal code channels for CDMA, (2) time slots forTDMA, or (3) sub-bands for OFDM. A CDMA system may implement IS-2000,IS-95, IS-856, Wideband-CDMA (W-CDMA), or some other standards. An OFDMsystem may implement Institute of Electrical and Electronics Engineers(IEEE) 802.11 (Wireless Local Area Network (WLAN)), IEEE 802.16(Worldwide Interoperability for Microwave Access (WiMAX)), Long TermEvolution (LTE) (e.g., in TDD and/or FDD modes), or some otherstandards. A TDMA system may implement Global System for MobileCommunications (GSM) or some other standards. These various standardsare known in the art. The techniques described herein may also beimplemented in any of various other suitable wireless systems usingradio frequency (RF) technology, including Global Navigation SatelliteSystem (GNSS), Bluetooth, IEEE 802.15 (Wireless Personal Area Network(WPAN)), Near Field Communication (NFC), Small Cell, FrequencyModulation (FM), and the like.

An Example Wireless System

FIG. 1 illustrates a wireless communications system 100 with accesspoints and user terminals. For simplicity, only one access point 110 isshown in FIG. 1. An access point (AP) is generally a fixed station thatcommunicates with the user terminals and may also be referred to as abase station (BS), an evolved Node B (eNB), or some other terminology. Auser terminal (UT) may be fixed or mobile and may also be referred to asa mobile station (MS), an access terminal, user equipment (UE), astation (STA), a client, a wireless device, or some other terminology. Auser terminal may be a wireless device, such as a cellular phone, apersonal digital assistant (PDA), a handheld device, a wireless modem, alaptop computer, a tablet, a personal computer, etc.

Access point 110 may communicate with one or more user terminals 120 atany given moment on the downlink and uplink. The downlink (i.e., forwardlink) is the communication link from the access point to the userterminals, and the uplink (i.e., reverse link) is the communication linkfrom the user terminals to the access point. A user terminal may alsocommunicate peer-to-peer with another user terminal. A system controller130 couples to and provides coordination and control for the accesspoints.

System 100 employs multiple transmit and multiple receive antennas fordata transmission on the downlink and uplink. Access point 110 may beequipped with a number N_(ap) of antennas to achieve transmit diversityfor downlink transmissions and/or receive diversity for uplinktransmissions. A set N_(u) of selected user terminals 120 may receivedownlink transmissions and transmit uplink transmissions. Each selecteduser terminal transmits user-specific data to and/or receivesuser-specific data from the access point. In general, each selected userterminal may be equipped with one or multiple antennas (i.e., N_(ut)≧1).The N_(u) selected user terminals can have the same or different numberof antennas.

Wireless system 100 may be a time division duplex (TDD) system or afrequency division duplex (FDD) system. For a TDD system, the downlinkand uplink may share the same frequency band. For an FDD system, thedownlink and uplink use different frequency bands. System 100 may alsoutilize a single carrier or multiple carriers for transmission. Eachuser terminal may be equipped with a single antenna (e.g., in order tokeep costs down) or multiple antennas (e.g., where the additional costcan be supported).

FIG. 2 shows a block diagram of access point 110 and two user terminals120 m and 120 x in wireless system 100. Access point 110 is equippedwith N_(ap) antennas 224 a through 224 ap. User terminal 120 m isequipped with N_(ut,m) antennas 252 ma through 252 mu, and user terminal120 x is equipped with N_(ut,x) antennas 252 xa through 252 xu. Accesspoint 110 is a transmitting entity for the downlink and a receivingentity for the uplink. Each user terminal 120 is a transmitting entityfor the uplink and a receiving entity for the downlink. As used herein,a “transmitting entity” is an independently operated apparatus or devicecapable of transmitting data via a frequency channel, and a “receivingentity” is an independently operated apparatus or device capable ofreceiving data via a frequency channel. In the following description,the subscript “dn” denotes the downlink, the subscript “up” denotes theuplink, N_(up) user terminals are selected for simultaneous transmissionon the uplink, N_(dn) user terminals are selected for simultaneoustransmission on the downlink, N_(up) may or may not be equal to N_(dn),and N_(up) and N_(dn) may be static values or can change for eachscheduling interval. Beam-steering or some other spatial processingtechnique may be used at the access point and user terminal.

On the uplink, at each user terminal 120 selected for uplinktransmission, a TX data processor 288 receives traffic data from a datasource 286 and control data from a controller 280. TX data processor 288processes (e.g., encodes, interleaves, and modulates) the traffic data{d_(up)} for the user terminal based on the coding and modulationschemes associated with the rate selected for the user terminal andprovides a data symbol stream {s_(up)} for one of the N_(ut,m) antennas.A transceiver front-end (TX/RX) 254 (also known as a radio frequencyfront-end (RFFE)) receives and processes (e.g., converts to analog,amplifies, filters, and frequency upconverts) a respective symbol streamto generate an uplink signal. The transceiver front-end 254 may alsoroute the uplink signal to one of the N_(ut,m) antennas for transmitdiversity via an RF switch, for example. The controller 280 may controlthe routing within the transceiver front-end 254.

A number N_(up) of user terminals may be scheduled for simultaneoustransmission on the uplink. Each of these user terminals transmits itsset of processed symbol streams on the uplink to the access point.

At access point 110, N_(ap) antennas 224 a through 224 ap receive theuplink signals from all N_(up) user terminals transmitting on theuplink. For receive diversity, a transceiver front-end 222 may selectsignals received from one of the antennas 224 for processing. Forcertain aspects of the present invention, a combination of the signalsreceived from multiple antennas 224 may be combined for enhanced receivediversity. The access point's transceiver front-end 222 also performsprocessing complementary to that performed by the user terminal'stransceiver front-end 254 and provides a recovered uplink data symbolstream. The recovered uplink data symbol stream is an estimate of a datasymbol stream {s_(up)} transmitted by a user terminal. An RX dataprocessor 242 processes (e.g., demodulates, deinterleaves, and decodes)the recovered uplink data symbol stream in accordance with the rate usedfor that stream to obtain decoded data. The decoded data for each userterminal may be provided to a data sink 244 for storage and/or acontroller 230 for further processing.

On the downlink, at access point 110, a TX data processor 210 receivestraffic data from a data source 208 for N_(dn) user terminals scheduledfor downlink transmission, control data from a controller 230 andpossibly other data from a scheduler 234. The various types of data maybe sent on different transport channels. TX data processor 210 processes(e.g., encodes, interleaves, and modulates) the traffic data for eachuser terminal based on the rate selected for that user terminal TX dataprocessor 210 may provide a downlink data symbol streams for one of moreof the N_(dn) user terminals to be transmitted from one of the N_(ap)antennas. The transceiver front-end 222 receives and processes (e.g.,converts to analog, amplifies, filters, and frequency upconverts) thesymbol stream to generate a downlink signal. The transceiver front-end222 may also route the downlink signal to one or more of the N_(ap)antennas 224 for transmit diversity via an RF switch, for example. Thecontroller 230 may control the routing within the transceiver front-end222.

At each user terminal 120, N_(ut,m) antennas 252 receive the downlinksignals from access point 110. For receive diversity at the userterminal 120, the transceiver front-end 254 may select signals receivedfrom one of the antennas 252 for processing. For certain aspects of thepresent invention, a combination of the signals received from multipleantennas 252 may be combined for enhanced receive diversity. The userterminal's transceiver front-end 254 also performs processingcomplementary to that performed by the access point's transceiverfront-end 222 and provides a recovered downlink data symbol stream. AnRX data processor 270 processes (e.g., demodulates, deinterleaves, anddecodes) the recovered downlink data symbol stream to obtain decodeddata for the user terminal.

Those skilled in the art will recognize the techniques described hereinmay be generally applied in systems utilizing any type of multipleaccess schemes, such as TDMA, SDMA, Orthogonal Frequency DivisionMultiple Access (OFDMA), CDMA, SC-FDMA, and combinations thereof.

FIG. 3 is a block diagram of an example transceiver front-end 300, suchas transceiver front-ends 222, 254 in FIG. 2. The transceiver front-end300 includes a transmit (TX) path 302 (also known as a transmit chain)for transmitting signals via one or more antennas and a receive (RX)path 304 (also known as a receive chain) for receiving signals via theantennas. When the TX path 302 and the RX path 304 share an antenna 303,the paths may be connected with the antenna via an interface 306, whichmay include any of various suitable RF devices, such as a duplexer, aswitch, a diplexer, and the like.

Receiving in-phase (I) or quadrature (Q) baseband analog signals from adigital-to-analog converter (DAC) 308, the TX path 302 may include abaseband filter (BBF) 310, a mixer 312, a driver amplifier (DA) 314, anda power amplifier 316. The BBF 310, the mixer 312, and the DA 314 may beincluded in a radio frequency integrated circuit (RFIC), while the PA316 is often external to the RFIC. The BBF 310 filters the basebandsignals received from the DAC 308, and the mixer 312 mixes the filteredbaseband signals with a transmit local oscillator (LO) signal to convertthe baseband signal of interest to a different frequency (e.g.,upconvert from baseband to RF). This frequency conversion processproduces the sum and difference frequencies of the LO frequency and thefrequency of the signal of interest. The sum and difference frequenciesare referred to as the beat frequencies. The beat frequencies aretypically in the RF range, such that the signals output by the mixer 312are typically RF signals, which are amplified by the DA 314 and by thePA 316 before transmission by the antenna 303.

The RX path 304 includes a low noise amplifier (LNA) 322, a mixer 324,and a baseband filter (BBF) 326. The LNA 322, the mixer 324, and the BBF326 may be included in a radio frequency integrated circuit (RFIC),which may or may not be the same RFIC that includes the TX pathcomponents. RF signals received via the antenna 303 may be amplified bythe LNA 322, and the mixer 324 mixes the amplified RF signals with areceive local oscillator (LO) signal to convert the RF signal ofinterest to a different baseband frequency (i.e., downconvert). Thebaseband signals output by the mixer 324 may be filtered by the BBF 326before being converted by an analog-to-digital converter (ADC) 328 todigital I or Q signals for digital signal processing.

While it is desirable for the output of a LO to remain stable infrequency, tuning to different frequencies indicates using avariable-frequency oscillator, which involves compromises betweenstability and tunability. Contemporary systems employ frequencysynthesizers with a voltage-controlled oscillator (VCO) to generate astable, tunable LO with a particular tuning range. Thus, the transmit LOis typically produced by a TX frequency synthesizer 318, which may bebuffered or amplified by amplifier 320 before being mixed with thebaseband signals in the mixer 312. Similarly, the receive LO istypically produced by an RX frequency synthesizer 330, which may bebuffered or amplified by amplifier 332 before being mixed with the RFsignals in the mixer 324.

Example Phase Detecting Circuit

FIG. 4 illustrates an example phase detecting circuit 400. The phasedetecting circuit 400 may be used to determine whether two input signals(v_(in,1) and v_(in,2)) are in-phase or out-of-phase and output anindication thereof. The two input signals may be oscillating signalshaving the same frequency, which may be in the RF range. The phasedetecting circuit 400 may include a mixer 402, a filtering capacitor404, and a comparator 406 as shown in FIG. 4. For other aspects, thephase detecting circuit 400 may include a multi-bit analog-to-digitalconverter (ADC) (not shown) instead of or in addition to the comparator406 (which can be considered as a single-bit ADC). For ease ofdescription, the present disclosure refers to a comparator, but a personhaving ordinary skill in the art will understand that a multi-bit ADCmay be used instead of a 1-bit ADC (i.e., the comparator).

The mixer 402 effectively multiplies the two input signals together,thereby producing an output signal having frequency components at thesum of and the difference of the two input signals' frequencies. If thetwo input signals have the same frequency, then the output signal hasfrequency components at DC and at twice the frequency of the inputsignal. For example, if the input signals are oscillating signals with afrequency of 2 GHz, then the output signal has frequency components atDC and at 4 GHz.

The mixer 402 may be implemented with a double-balanced mixer, such as aGilbert cell. Using bipolar junction transistors (BJTs), the Gilbertcell may be realized using two cross-coupled emitter-coupled pairs oftransistors in series with an emitter-coupled pair of transistors, asunderstood by a person skilled in the art of RF electronics. Afunctionally equivalent mixer circuit to the Gilbert cell may also beimplemented using JFETs or MOSFETs, for example, instead of BJTs. Whentwo unmodulated signals of identical frequency are applied to the twoinputs of the Gilbert cell, this circuit behaves as a phase detector andproduces an output whose DC component is proportional to the phasedifference between the two input signals. The frequency component attwice the input frequency is filtered out using a low-pass filter, suchas the filtering capacitor 404, thereby leaving only the DC component atthe output of the filter.

The comparator 406 compares the DC component at the output of thefiltering capacitor 404 to a reference signal 408. As used herein, thereference signal generally refers to the signal at the negative terminalof the comparator. If the amplitude of the DC component is above theamplitude of the reference signal (typically by a certain threshold foran expected phase shift range around 0°), then the comparator outputs alogic HIGH (a binary “1”), and the two input signals (v_(in,1) andv_(in,2)) are determined to be in-phase. In contrast, if the amplitudeof the DC component is below the amplitude of the reference signal(typically by a certain threshold for an expected phase shift rangearound 180°), then the comparator outputs a logic LOW (a binary “0”),and the two input signals (v_(in,1) and v_(in,2)) are determined to beout-of-phase. For certain aspects, the inputs to the comparator 406 maybe flipped to have the opposite binary logic. For certain aspects, thecomparator 406 may be a clocked regenerative comparator.

As described above, the comparator 406 may be thought of as a 1-bit ADC.For certain aspects, the comparator is a circuit forming part of an ADC.For example, the ADC may be a multi-bit ADC configured to provideinformation in addition to a determination whether the first inputsignal is in-phase or out-of-phase with the second input signal. Thisadditional information may indicate the degree to which the first andsecond input signals are phase shifted.

For certain aspects as illustrated in FIG. 4, the input signals and theoutput signal of the mixer 402 may be differential signals. In thiscase, the filtering capacitor 404 may shunt a first output signal and asecond output signal of a differential pair for the output signal,thereby generating a first DC component and a second DC component,respectively. In this case, the second output signal is the referencesignal 408, and the comparator 406 compares the first DC component tothe second DC component. The first input signal (v_(in,1)) is determinedto be in-phase with the second input signal (v_(in,2)) if the first DCcomponent has a greater amplitude than the second DC component, whilethe first input signal (v_(in,1)) is determined to be out-of-phase withthe second input signal (v_(in,2)) if the second DC component has agreater amplitude than the first DC component.

Example Interchain Lo Divider Phase Detection and Alignment

The phase detecting circuit 400 described above may be used to detectphase shifts between LO signals in two different radio frequency (RF)chains, for example. As described above, the RF chains may be RX chains,TX chains, or transceiver chains.

FIG. 5 is a block diagram illustrating two adjacent RF chains (labeled“Chain N” and “Chain N+1”) in a multi-chain RFFE. A frequencysynthesizer 502 (e.g., the TX frequency synthesizer 318 or the RXfrequency synthesizer 330) may generate an oscillating signal (which maybe referred to as a “VCO signal”) using a VCO 504 and supportingcircuitry. Each RF chain may generate its own LO using a divide-by-2(Div2) frequency divider 506 and an amplifier 508. Each divider 506 mayarbitrarily start-up either in-phase (0°) or out-of-phase (180°)relative to a divider in another RF chain. The amplifier 508 may be usedto amplify, buffer, or attenuate the frequency-divided output signal ofthe divider 506 to generate the LO for each chain.

A repeater 510 may be used to regenerate the VCO signal from one RFchain to the next. Unfortunately, the repeater may also introduce aphase shift between the signals input to the frequency dividers 506 ineach RF chain.

The LO from one RF path (Chain N) may be input as the first input signalto the phase detecting circuit 400, and the LO from an adjacent RF path(Chain N+1) may be input as the second input signal to the phasedetecting circuit. The phase detecting circuit 400 may be used todetermine whether the LO in Chain N is in-phase or out-of-phase with theLO in Chain N+1 and output a binary indication based on thisdetermination. Digital logic (e.g., XOR gates) may be used to determinewhich of the multiple LO signals should be phase adjusted. The digitallogic may drive multiplexers (not shown), one in each RF chain, toselect between normal (e.g., pass-through) and polarity-flipped signalsin an effort to phase adjust the LO signals. The multiplexers may belocated between the frequency dividers 506 and the amplifiers 508.

As an example, if an RFFE has four RF paths referred to as Chain 0, 1,2, and 3 where Chain 1 is adjacent to Chain 0, Chain 2 is adjacent toChain 1, and Chain 3 is adjacent to Chain 2, then Chains 1, 2, and 3 mayeach contain a phase detecting circuit 400. For certain aspects, Chain 0may also include a phase detecting circuit 400 (e.g., for ease ofrepeating the same layout for all of these four RF paths), but thiscircuit may be deactivated.

FIG. 6 is an example graph 600 of the voltage difference (V_(φ,diff))between the differential signal pair output by the mixer 402 andfiltered by the capacitor 404 versus phase offset in degrees forparticular process, voltage and, temperature (PVT) variations. A firstexpected phase shift range 602 (e.g., between 0° and 67°) correspondingto the LO signal from Chain N being in-phase with the LO signal fromChain N+1 leads to the voltage difference (V_(φ,diff)) being above afirst threshold (e.g., 0.3 V). A second expected phase shift range 604(e.g., between 180° and 247°) corresponding to the LO signal from ChainN being out-of-phase with the LO signal from Chain N+1 leads to thevoltage difference (V_(φ,diff)) being below a second threshold (e.g.,−0.3 V).

Example Phase Detecting Operations

FIG. 7 is a flow diagram of example operations 700 for detecting phaseshift between signals. The operations 700 may be performed, at least inpart, by a phase detector, such as the phase detecting circuit 400depicted in FIGS. 4 and 5.

The operations 700 may begin, at block 702, with a mixer (e.g., themixer 402) mixing a first input signal having a first frequency with asecond input signal having a second frequency to produce an outputsignal having frequency components at the sum of and the differencebetween the first frequency and the second frequency. The firstfrequency is the same as the second frequency. For certain aspects, themixing at block 702 involves using a Gilbert cell to mix the first inputsignal with the second input signal.

At block 704, a filter (e.g., the capacitor 404) may filter the outputsignal produced by the mixer to remove one of the frequency componentsat the sum of the first frequency and the second frequency. Thisfiltering leaves a direct current (DC) component (i.e., the differencebetween the first and second frequencies, which are the same).

An ADC (e.g., the comparator 406, which is a 1-bit ADC) may compare theDC component to a reference signal at block 706. At block 708, digitallogic or a processing unit, for example, may determine whether the firstinput signal is in-phase or out-of-phase with the second input signalbased on the comparison at block 706.

According to certain aspects, the first, second, and output signals aredifferential signals. In this case, the filtering at block 704 mayinclude using a capacitor to shunt a first output signal and a secondoutput signal of a differential pair for the output signal to generate afirst DC component and a second DC component, respectively. For certainaspects, the comparing at block 706 involves comparing the first outputsignal to the second output signal, where the second output signal isthe reference signal. The first input signal may be determined to bein-phase with the second input signal if the first DC component has agreater amplitude than the second DC component (e.g., as shown in thegraph 600 of FIG. 6). In the alternative, the first input signal may bedetermined to be out-of-phase with the second input signal if the secondDC component has a greater amplitude than the first DC component.

According to certain aspects, a first expected phase shift rangecorresponding to the first input signal being in-phase with the secondinput signal may lead to an amplitude of the DC component being above afirst threshold. Similarly, a second expected phase shift rangecorresponding to the first input signal being out-of-phase with thesecond input signal may lead to the amplitude of the DC component beingbelow a second threshold.

According to certain aspects, the first input signal is a first localoscillating signal of a first transceiver path. The second input signalmay be a second local oscillating signal of a second transceiver pathadjacent to the first transceiver path. In this case, the operations 700may further involve a first frequency dividing circuit (e.g., thefrequency divider 506) frequency dividing a VCO signal to generate thefirst local oscillating signal. A repeater (e.g., the LO repeater 510)may regenerate the VCO signal to generate a repeated oscillating signal,and a second frequency dividing circuit may frequency divide therepeated oscillating signal to generate the second local oscillatingsignal.

According to certain aspects, the operations 700 may further involve aphase shifting circuit phase shifting at least one of the first inputsignal or the second input signal if the first input signal isdetermined to be out-of-phase with the second input signal.

According to certain aspects, the operations 700 may further includeproviding information in addition to a determination whether the firstinput signal is in-phase or out-of-phase with the second input signal.For example, the information may indicate a degree to which the firstand second input signals are phase shifted.

Example Synchronized Reset for LO Divider Phase Alignment

FIG. 8 is a block diagram illustrating two adjacent RF chains, similarto “Chain N” and “Chain N+1” in FIG. 5. As described above, the RFchains may be RX chains, TX chains, or transceiver chains. Each RF chainmay generate its own local oscillator (LO) using a frequency divider802, which may have multiple frequency division options (e.g., Div2,Div3, and Div4). For example, in high-band (e.g., 5 GHz) mode, thefrequency divider 802 may operate in Div2 mode. In low-band (e.g., 2.4GHz) mode, however, the frequency divider may operate in either Div2 orDiv3 mode. In Div2 mode, each frequency divider 802 may arbitrarilystart-up either in-phase (0°) or out-of-phase (180°) relative to afrequency divider in another RF chain. In Div3 mode, each frequencydivider 802 may arbitrarily start-up with a phase shift of 0°, 60°,120°, 180°, 240°, or 300° relative to a frequency divider in another RFchain. For the Div3 mode, the phase detecting and adjusting describedabove for the Div2 mode may not be effective in phase aligning thefrequency-divided signals in the multiple RF chains.

Certain aspects of the present invention perform a synchronized reset toforce the frequency dividers 802 to start up in-phase. Phase alignmentin the Div2 mode may also be achieved through phase detection and outputpolarity flipping as described above. Both Div2 phase alignment schemesmay be implemented in an RFFE for robustness, but the synchronized resetscheme is invoked to achieve phase alignment for the Div3 mode (as wellas other higher frequency-division modes).

As described above, a frequency synthesizer 502 (e.g., the TX frequencysynthesizer 318 or the RX frequency synthesizer 330) may generate anoscillating signal (which may be referred to as a “VCO signal”) using aVCO 504 and supporting circuitry. In FIG. 8, the VCO signal (or arepeated version thereof) may be buffered by amplifier 804 in each RFchain. The local synthesizer output “clock” signal 803 (labeled “LocalLO Clock”) output by the amplifier 804 may drive the LO circuitry ineach RF chain (e.g., the closest RF chain to the frequency synthesizer502, referred to as “Chain 0”). A local synthesizer output clock signal803 is similarly generated in each RF chain. In each RF chain, the localsynthesizer clock signal 803 is divided by 2 or by 3 by the frequencydivider 802 to generate a frequency-divided signal 908 (also referred toas a local oscillator (LO) and illustrated in FIG. 9) for thatparticular RF chain, and it is these LOs for the RF chains that arephase aligned by certain aspects of the present invention.

In each RF chain, the local synthesizer clock signal 803 may bere-buffered at repeater 806 (labeled “LO Repeater”) and transmitted tothe next closest transceiver chain (e.g., “Chain 1”). In this manner,the VCO signal may be distributed in a daisy chain, e.g., from theclosest RF chain to the furthest RF chain.

In certain instances (e.g., when the frequency synthesizer 502 starts upor changes one or more operating parameters, such as channels), a phasesynchronization reset pulse is generated by a digital controller 807(labeled “DTop” in FIG. 8). The digital controller may be part of thefrequency synthesizer 502 for certain aspects. This reset pulse istransmitted to Chain 0 and received by synchronization logic 808. Thesynchronization logic 808 retimes the reset pulse to the localsynthesizer clock signal using flip-flops, for example. FIG. 9illustrates an example implementation of the synchronization logic 808with flip-flops. The retimed signal drives the reset input of the localfrequency divider 802 and is also appropriately delayed, buffered, andthen transmitted to the next RF chain.

In FIG. 9, the reset pulse is received at the synchronization logic 808(namely, at “Rst In”) from the digital controller 807 (or from anadjacent RF chain) and delayed by a pair of flip-flops 902 (e.g., delay(D) flip-flops). The pair of flip-flops 902 may prevent metastability inthe RF chain. The output from the pair of flip-flops 902 drives a set offlip-flops 904 to produce the retimed rest pulse at the output (labeled“Rst Out”) of the synchronization logic 808. Because the flip-flops inthe synchronization logic 808 for a given RF chain are clocked by thesynthesizer clock signal 803 for that RF chain, the retimed reset pulseis synchronized to the synthesizer clock signal. This daisy-chained,retimed reset out to the next RF chain relaxes the reset propagationtiming specifications relative to propagation of the synthesizer clocksignal (Local LO Clock).

As illustrated in the example of FIG. 9, there are a total of sixcascaded flip-flops along the path 905 from the input to the output ofthe synchronization logic 808. This 6-cycle delay from Rst In to Rst Outcontrols the start-up timing of the frequency divider 802 in the next RFchain to be in-phase with this RF chain, whether in Div2 or Div3 mode.This is because 6 is the least common multiple (LCM) of 2 and 3. Thisphenomenon is illustrated in the timing diagram 910, where “Clk”represents the synthesizer clock signal (Local LO Clock). After 6 Clkcycles, the output of a frequency divider reset in the next RF chain andoperating in either Div2 (represented by “/2 Out”) or Div3 (representedby “/3 Out”) will be in-phase with the output of a frequency dividerreset in the current RF chain. Alternatively for certain aspects, thenumber of flip-flops along the path 905 may be 12 or 18, for example. Ifa number of flip-flops along the path 905 is different (e.g., 3 or 4flip-flops) than a common multiple of the frequency-division modes, thenthe outputs of frequency dividers in different RF chains may not be inphase, as illustrated in the timing diagram 910 for 1, 2, 3, 4, or 5 Clkcycles.

The output from the pair of flip-flops 902 may also drive another set offlip-flops 906 to produce the local reset signal (labeled “Rst”) for thefrequency divider 802 in the current RF chain. The local frequencydivider 802 may be a CMOS divider capable of fast, timed start-up andresets. The set of flips-flops 906 may be used to gradually boost theRst drive strength. Any suitable number of flip-flops (e.g., in a rangefrom 2 to 10) may be used in this set 906. For certain aspects, this setof flip-flops 906 may be driven from an output of one of the flip-flopsin the set of flip-flops 904, rather than from the output of the pair offlip-flops 902, such as after the second flip-flop in the set offlip-flops 904.

Through careful design of the propagation delay of the retimed resetpulse relative to the phase shift of the VCO signal as it travels fromchain to chain, the reset pulse forces the frequency divider 802 inChain 1 to start up in phase with its counterpart in Chain 0. A retimedreset pulse is similarly transmitted from Chain 1 to Chain 2 and fromChain 2 to Chain 3, in order to phase synchronize the LOs (thefrequency-divided signals 908) output by the frequency dividers 802 inall four RF chains. Such phase alignment may provide for implicitbeam-forming with fast channel switching and/or prevent multi-modal RXpath DC offsets caused by mixing with arbitrary-phase divider spurs.

Compared to the phase detecting and adjusting scheme, thesynchronization reset scheme forces in-phase start-up, instead of usingphase detection and separate phase correction circuitry, which maydegrade phase noise, use more area, and consume more power incomparison. The synchronized reset scheme employs single-ended resetsignaling between RF chains, rather than driving differential divideroutputs between RF chains for phase comparison. Furthermore, thesynchronized reset scheme supports phase aligning the outputs of Div2and Div3 frequency dividers (as well as other frequency division modes)and may employ a simpler digital controller.

FIG. 10 is a flow diagram of example operations 1000 for synchronizingfrequency-divided oscillating signals associated with multipletransceiver paths to be in-phase. The operations 1000 may be performed,at least in part, by resettable frequency dividers and synchronizationlogic, such as the components depicted in FIGS. 8 and 9.

The operations 1000 may begin, at block 1002, with a first distributioncircuit providing a first oscillating signal for a first transceiverpath.

At block 1004, first synchronization logic may receive a first globalreset signal. The first synchronization logic may delay the first globalreset signal by clocking with the first oscillating signal to generate afirst local reset signal synchronized to the first oscillating signal atblock 1006.

At block 1008, a first frequency divider may frequency divide the firstoscillating signal to generate a first frequency-divided signal for thefirst transceiver path. For example, the first frequency divider mayfrequency divide the first oscillating signal by 2 or by 3. The firstfrequency divider may alternatively or additionally frequency divide thefirst oscillating signal by a divisor other than 2 or 3. The first localreset signal may reset the first frequency divider to reset thefrequency dividing of the first oscillating signal.

At block 1010, the first synchronization logic may output a secondglobal reset signal synchronized to the first oscillating signal.

A second distribution circuit may provide a second oscillating signalfor a second transceiver path at block 1012. The second oscillatingsignal has the same frequency as the first oscillating signal. The firsttransceiver path may be adjacent to the second transceiver path.

At block 1014, second synchronization logic may delay the second globalreset signal by clocking with the second oscillating signal to generatea second local reset signal synchronized to the second oscillatingsignal.

At block 1016, a second frequency divider may frequency divide thesecond oscillating signal to generate a second frequency-divided signalfor the second transceiver path. The second local reset signal may resetthe second frequency divider to reset the frequency dividing of thesecond oscillating signal such that the second frequency-divided signalis in-phase with the first frequency-divided signal.

According to certain aspects, the operations 1000 may further involvegenerating a synthesized oscillating signal from a frequencysynthesizer. The first distribution circuit may include a buffer, and inthis case, providing the first oscillating signal at block 1002 mayentail buffering the synthesized oscillating signal with the buffer. Thefirst distribution circuit may include a repeater, in which caseproviding the first oscillating signal may involve regenerating thesynthesized oscillating signal, or a regenerated version thereof, from athird transceiver path. For certain aspects, receiving the first globalreset signal at block 1004 is in response to the frequency synthesizerstarting up or changing one or more operating parameters (e.g., wirelesschannels, which may indicate changing the frequency of the synthesizedoscillating signal output by the frequency synthesizer).

According to certain aspects, receiving the first global reset signal atblock 1004 involves receiving the first global reset signal from a thirdtransceiver path. In this case, the first global reset signal may besynchronized to a third oscillating signal for the third transceiverpath.

According to certain aspects, the operations 1000 may further involvederiving the second oscillating signal from the first oscillatingsignal. For example, the second oscillating signal may be a regeneratedand buffered version of the first oscillating signal.

According to certain aspects, outputting the second global reset signalat block 1010 entails delaying the first global reset signal by clockingwith the first oscillating signal a multiple of a least common multiple(LCM) between divisor options for the frequency dividing of the firstoscillating signal. For certain aspects, the divisor options are 2 and 3(i.e., Div2 and Div3), the LCM is 6, and the first global reset signalis delayed 6 times (e.g., clock cycles) by clocking 6 cascaded delay (D)flip-flops with the first oscillating signal. Other divisor options(e.g., besides or in addition to the combination of 2 and 3) may be usedfor other aspects.

According to certain aspects, the operations 1000 may further involvethe second synchronization logic outputting a third global reset signalsynchronized to the second oscillating signal. A third distributioncircuit may provide a third oscillating signal for a third transceiverpath, where the third oscillating signal has the same frequency as thefirst and second oscillating signals. Third synchronization logic maydelay the third global reset signal by clocking with the thirdoscillating signal to generate a third local reset signal synchronizedto the third oscillating signal. A third frequency divider may frequencydivide the third oscillating signal to generate a thirdfrequency-divided signal for the third transceiver path. The third localreset signal may reset the third frequency divider to reset thefrequency dividing of the third oscillating signal such that the thirdfrequency-divided signal is in phase with the first and secondfrequency-divided signals. In this case, the first transceiver path maybe adjacent to the second transceiver path, and the second transceiverpath may be adjacent to the third transceiver path.

The various operations or methods described above may be performed byany suitable means capable of performing the corresponding functions.The means may include various hardware and/or software component(s)and/or module(s), including, but not limited to a circuit, anapplication specific integrated circuit (ASIC), or processor. Generally,where there are operations illustrated in figures, those operations mayhave corresponding counterpart means-plus-function components withsimilar numbering.

For example, means for transmitting may comprise a transmitter (e.g.,the transceiver front-end 254 of the user terminal 120 depicted in FIG.2 or the transceiver front-end 222 of the access point 110 shown in FIG.2) and/or an antenna (e.g., the antennas 252 ma through 252 mu of theuser terminal 120 m portrayed in FIG. 2 or the antennas 224 a through224 ap of the access point 110 illustrated in FIG. 2). Means forreceiving may comprise a receiver (e.g., the transceiver front-end 254of the user terminal 120 depicted in FIG. 2 or the transceiver front-end222 of the access point 110 shown in FIG. 2) and/or an antenna (e.g.,the antennas 252 ma through 252 mu of the user terminal 120 m portrayedin FIG. 2 or the antennas 224 a through 224 ap of the access point 110illustrated in FIG. 2). Means for processing or means for determiningmay comprise a processing system, which may include one or moreprocessors, such as the RX data processor 270, the TX data processor288, and/or the controller 280 of the user terminal 120 illustrated inFIG. 2. Means for mixing may include a mixing circuit, such as the mixer402 in FIG. 4. Means for frequency dividing may include a frequencydividing circuit, such as the Div2 frequency dividers 506 in FIG. 5.Means for filtering may include any suitable filtering circuit includingactive and/or passive filters, such as the capacitor 404 in FIG. 4.Means for comparing may include a comparing circuit, such as an ADC orthe comparator 406 in FIG. 4. Means for phase shifting may include aphase shifting circuit, such as a multiplexer configured to selectbetween pass-through and polarity flipped output signals. Means forregenerating or means for deriving may include a repeating circuit, suchas the LO repeater 510 in FIG. 5.

As used herein, the term “determining” encompasses a wide variety ofactions. For example, “determining” may include calculating, computing,processing, deriving, investigating, looking up (e.g., looking up in atable, a database or another data structure), ascertaining and the like.Also, “determining” may include receiving (e.g., receiving information),accessing (e.g., accessing data in a memory) and the like. Also,“determining” may include resolving, selecting, choosing, establishingand the like.

As used herein, a phrase referring to “at least one of” a list of itemsrefers to any combination of those items, including single members. Asan example, “at least one of: a, b, or c” is intended to cover: a, b, c,a-b, a-c, b-c, a-b-c, as well as any combination with multiples of thesame element (e.g., a-a, a-a-a, a-a-b, a-a-c, a-b-b, a-c-c, b-b, b-b-b,b-b-c, c-c, and c-c-c or any other ordering of a, b, and c).

The various illustrative logical blocks, modules and circuits describedin connection with the present invention may be implemented or performedwith a general purpose processor, a digital signal processor (DSP), anapplication specific integrated circuit (ASIC), a field programmablegate array (FPGA) or other programmable logic device (PLD), discretegate or transistor logic, discrete hardware components, or anycombination thereof designed to perform the functions described herein.A general-purpose processor may be a microprocessor, but in thealternative, the processor may be any commercially available processor,controller, microcontroller, or state machine. A processor may also beimplemented as a combination of computing devices, e.g., a combinationof a DSP and a microprocessor, a plurality of microprocessors, one ormore microprocessors in conjunction with a DSP core, or any other suchconfiguration.

The methods disclosed herein comprise one or more steps or actions forachieving the described method. The method steps and/or actions may beinterchanged with one another without departing from the scope of theclaims. In other words, unless a specific order of steps or actions isspecified, the order and/or use of specific steps and/or actions may bemodified without departing from the scope of the claims.

The functions described may be implemented in hardware, software,firmware, or any combination thereof. If implemented in hardware, anexample hardware configuration may comprise a processing system in awireless node. The processing system may be implemented with a busarchitecture. The bus may include any number of interconnecting busesand bridges depending on the specific application of the processingsystem and the overall design constraints. The bus may link togethervarious circuits including a processor, machine-readable media, and abus interface. The bus interface may be used to connect a networkadapter, among other things, to the processing system via the bus. Thenetwork adapter may be used to implement the signal processing functionsof the PHY layer. In the case of a user terminal 120 (see FIG. 1), auser interface (e.g., keypad, display, mouse, joystick, etc.) may alsobe connected to the bus. The bus may also link various other circuitssuch as timing sources, peripherals, voltage regulators, powermanagement circuits, and the like, which are well known in the art, andtherefore, will not be described any further.

The processing system may be configured as a general-purpose processingsystem with one or more microprocessors providing the processorfunctionality and external memory providing at least a portion of themachine-readable media, all linked together with other supportingcircuitry through an external bus architecture. Alternatively, theprocessing system may be implemented with an ASIC (Application SpecificIntegrated Circuit) with the processor, the bus interface, the userinterface in the case of an access terminal), supporting circuitry, andat least a portion of the machine-readable media integrated into asingle chip, or with one or more FPGAs (Field Programmable Gate Arrays),PLDs (Programmable Logic Devices), controllers, state machines, gatedlogic, discrete hardware components, or any other suitable circuitry, orany combination of circuits that can perform the various functionalitydescribed throughout this disclosure. Those skilled in the art willrecognize how best to implement the described functionality for theprocessing system depending on the particular application and theoverall design constraints imposed on the overall system.

It is to be understood that the claims are not limited to the preciseconfiguration and components illustrated above. Various modifications,changes and variations may be made in the arrangement, operation anddetails of the methods and apparatus described above without departingfrom the scope of the claims.

4. The method of claim 2, wherein providing the first oscillating signalcomprises regenerating the synthesized oscillating signal, or aregenerated version thereof, from a third transceiver path.
 5. Themethod of claim 2, wherein receiving the first global reset signal is inresponse to the frequency synthesizer starting up or changing one ormore operating parameters.
 6. The method of claim 1, wherein receivingthe first global reset signal comprises receiving the first global resetsignal from a third transceiver path and wherein the first global resetsignal is synchronized to a third oscillating signal for the thirdtransceiver path.
 7. The method of claim 1, further comprising derivingthe second oscillating signal from the first oscillating signal.
 8. Themethod of claim 1, wherein outputting the second global reset signalcomprises delaying the first global reset signal by clocking with thefirst oscillating signal a multiple of a least common multiple (LCM)between divisor options for the frequency dividing of the firstoscillating signal, wherein the divisor options are 2 and 3, wherein theLCM is 6, and wherein the first global reset signal is delayed 6 timesby clocking 6 cascaded delay (D) flip-flops with the first oscillatingsignal.
 9. The method of claim 1, further comprising: outputting a thirdglobal reset signal synchronized to the second oscillating signal;providing a third oscillating signal for a third transceiver path,wherein the third oscillating signal has the same frequency as the firstoscillating signal and the second oscillating signal; delaying the thirdglobal reset signal by clocking with the third oscillating signal togenerate a third local reset signal synchronized to the thirdoscillating signal; and frequency dividing the third oscillating signalto generate a third frequency-divided signal for the third transceiverpath, wherein the third local reset signal resets the frequency dividingof the third oscillating signal such that the third frequency-dividedsignal is in phase with the first frequency-divided signal and thesecond frequency-divided signal.
 10. The method of claim 1, whereinfrequency dividing the first oscillating signal comprises dividing afrequency of the first oscillating signal by
 3. 11. A circuit forsynchronizing frequency-divided oscillating signals associated withmultiple transceiver paths to be in-phase, the circuit comprising: afirst distribution circuit configured to provide a first oscillatingsignal for a first transceiver path; first synchronization logicconfigured to: receive a first global reset signal; delay the firstglobal reset signal by clocking with the first oscillating signal togenerate a first local reset signal synchronized to the firstoscillating signal; and output a second global reset signal synchronizedto the first oscillating signal; a first frequency divider configured tofrequency divide the first oscillating signal to generate a firstfrequency-divided signal for the first transceiver path, wherein thefirst local reset signal is configured to reset the first frequencydivider; a second distribution circuit configured to provide a secondoscillating signal for a second transceiver path, wherein the secondoscillating signal has the same frequency as the first oscillatingsignal; second synchronization logic configured to delay the secondglobal reset signal by clocking with the second oscillating signal togenerate a second local reset signal synchronized to the secondoscillating signal; and a second frequency divider configured tofrequency divide the second oscillating signal to generate a secondfrequency-divided signal for the second transceiver path, wherein thesecond local reset signal is configured to reset the second frequencydivider such that the second frequency-divided signal is in phase withthe first frequency-divided signal.
 12. The circuit of claim 11, furthercomprising a frequency synthesizer configured to generate a synthesizedoscillating signal, wherein the first oscillating signal is based on thesynthesized oscillating signal.
 13. The circuit of claim 12, wherein thefirst distribution circuit comprises a buffer configured to buffer thesynthesized oscillating signal to provide the first oscillating signal.14. The circuit of claim 12, wherein the first distribution circuitcomprises a repeater configured to regenerate the synthesizedoscillating signal, or a regenerated version thereof, from a thirdtransceiver path.
 15. The circuit of claim 12, wherein the firstsynchronization logic is configured to receive the first global resetsignal in response to the frequency synthesizer starting up or changingone or more operating parameters.
 16. The circuit of claim 11, whereinthe first synchronization logic is configured to receive the firstglobal reset signal from a third transceiver path and wherein the firstglobal reset signal is synchronized to a third oscillating signal forthe third transceiver path.
 17. The circuit of claim 11, wherein thefirst synchronization logic is configured to output the second globalreset signal by delaying the first global reset signal via clocking withthe first oscillating signal a multiple of a least common multiple (LCM)between divisor options for the first frequency divider, wherein thedivisor options are 2 and 3, wherein the LCM is 6, and wherein the firstglobal reset signal is delayed 6 times by clocking 6 cascaded delay (D)flip-flops with the first oscillating signal.
 18. (canceled)
 19. Thecircuit of claim 11, wherein the first frequency divider is configuredto divide a frequency of the first oscillating signal by at least one of2 or
 3. 20. An apparatus for synchronizing frequency-divided oscillatingsignals associated with multiple transceiver paths to be in-phase, theapparatus comprising: means for providing a first oscillating signal fora first transceiver path; means for receiving a first global resetsignal; means for delaying the first global reset signal by clockingwith the first oscillating signal to generate a first local reset signalsynchronized to the first oscillating signal; means for frequencydividing the first oscillating signal to generate a firstfrequency-divided signal for the first transceiver path, wherein thefirst local reset signal is configured to reset the means for frequencydividing the first oscillating signal; means for outputting a secondglobal reset signal synchronized to the first oscillating signal; meansfor providing a second oscillating signal for a second transceiver path,wherein the second oscillating signal has the same frequency as thefirst oscillating signal; means for delaying the second global resetsignal by clocking with the second oscillating signal to generate asecond local reset signal synchronized to the second oscillating signal;and means for frequency dividing the second oscillating signal togenerate a second frequency-divided signal for the second transceiverpath, wherein the second local reset signal is configured to reset themeans for frequency dividing the second oscillating signal such that thesecond frequency-divided signal is in phase with the firstfrequency-divided signal.